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september 1999 preliminary ML6420 * triple/dual phase-equalized, low-pass video filter 1 general description the ML6420 monolithic bicmos 6th-order filters provide fixed frequency low pass filtering for video applications. these triple output phase-equalized filters are designed for input anti-aliasing filtering. cut-off frequencies are either 3.0, 5.5, 8.0, or 9.3mhz. each channel incorporates a 6th-order low-pass filter, a first order all-pass filter, and a 75w coax cable driver. a control pin (range) is provided to allow the inputs to swing to ground by providing a 0.5v offset to the input. the filters are powered from a single 5v supply, and can drive 1v p-p over 75w (0.5v to 1.5v), or 2v p-p over 150w (0.5v to 2.5v). ml 6420 block diagram features n 3.0, 5.5, 8.0, or 9.3 mhz bandwidth n 1x or 2x gain n 6th-order filter with equalizer n >40db stopband rejection n no external components or clocks n 10% maximum frequency accuracy over supply and temperature n <2% differential gain, <2 differential phase n <25ns group delay variation n drives 1v p-p into 75 w , or 2v p-p into 150 w n 5v 10% operation n ML6420 available with 6db gain * some packages are end of life 1x gain 2x gain ML6420-1 ML6420-3 ML6420-4 ML6420-5 ML6420-7 filter a 5.5mhz 8.0mhz 8.0mhz 5.5mhz 9.3mhz filter b 5.5mhz 8.0mhz 3.0mhz 2.5mhz 9.3mhz filter c 5.5mhz 8.0mhz 3.0mhz 2.5mhz 9.3mhz triple input/anti-aliasing video filter 15 5 6 4 buf 1x/2x buf all pass a v in a 10 v out a 3k 1k 3.33k 16 1 buf all pass b v in b 9 3 v out b 3.33k 2 14 buf all pass c v in c 7 v out c 3.33k v cc c 8 v cc b v cc 11 v cc a gndc 13 gnda 12 gnd gnd range gndb i bias i bias i bias 3k 1k 3k 1k low pass a low pass b low pass c 1x/2x buf 1x/2x buf
ML6420 2 pin configuration pin description pin name function 1 gndb ground pin for filter b 2v in c signal input to filter c. input impedance is 4k w . 3 gnd power and logic ground 4 gndc ground pin for filter c. 5v cc positive supply for bias circuit. 6v cc c power supply voltage for filter c. 7v out c output of filter c. drive is 1v p-p into 75 w (0.5v to 1.5v) or 2v p-p into 150 w (0.5v to 2.5v). 8v cc b power supply voltage for filter b. 9v out b output of filter b. drive is 1v p-p into 75 w (0.5v to 1.5v) or 2v p-p into 150 w (0.5v to 2.5v). 10 v out a output of filter a. drive is 1v p-p into 75 w (0.5v to 1.5v) or 2v p-p into 150 w (0.5v to 2.5v). pin name function 11 v cc a power supply voltage for filter a. 12 gnd power and logic ground. 13 gnda ground pin for filter a. 14 range input signal range select. for -1 to -4; when range is low (0), the input signal range is 0.5v to 2.5v, with an output range of 0.5v to 2.5v. when range is high (1) the input signal range is 0v to 2v, with an output range of 0.5v to 2.5v. for -5 to -12; when range is low (0), the input signal range is 0.5v to 1.5v, with an output range of 0.5v to 2.5v. when range is high (1) the input signal range is 0v to 1v, with an output range of 0.5v to 2.5v. 15 v in a signal input to filter a. input impedance is 4k w . 16 v in b signal input to filter b. input impedance is 4k w . 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 top view ML6420 16-pin wide soic (s16w) gndb v in c gnd gndc v cc v cc c v out c v cc b v in b v in a range gnda gnd v cc a v out a v out b
ML6420 3 electrical characteristics unless otherwise specified, v cc = 5v 10%, t a = operating temperature range, r l =75w or 150w, v out = 2v p-p for 150w load and v out = 1v p-p for 75w load (notes 1-3) symbol parameter conditions min typ max units general r in input impedance 3 4 5 k w dr/r in input r matching between filters a, b and c 2 % i bias input current ML6420 (C1 to C4) v in = 0.5v, range = low C80 a v in = 0.0v, range = high C125 a ML6420 v in = 0.5v, range = low 45 a (C5 toC7) v in = 0.0v, range = high C210 a small signal ML6420 (C1 to C4) v in = 100mv p-p at 100khz C0.5 0 0.5 db gain ML6420 v in = 100mv p-p at 100khz 5.5 6 6.5 db (C5 to C7) differential ML6420 (C1 to C4) v in = 1.8v 0.7v at 1 % 3.58 & 4.43 mhz gain ML6420 v in = 0.8v to 1.5v 1 % (C5 to C7) differential ML6420 (C1 to C4) v in = 1.8v 0.7v at 1 deg 3.58 & 4.43 mhz phase ML6420 v in = 0.8v to 1.5v 1 deg (C5 to C7) v in input range ML6420 (C1 to C4) range = 0, ground 0.5 2.5 v range = 1, v cc 0.0 2.0 v ML6420 range = 0, ground 0.5 1.5 v (C5 to C7) range = 1, v cc 0.0 1.0 v peak overshoot 2t, 0.7v p-p pulse 2.0 % crosstalk ML6420 (C1 to C4) f in = 3.58, f in = 4.43mhz 50 db ML6420 f in = 3.58, f in = 4.43mhz 45 db (C5 to C7) channel to channel f in = 100khz 10 ns group delay matching (f c = 5.5mhz) filters with identical f c channel to channel gain matching f in = 100khz 2 % absolute maximum ratings absolute maximum ratings are those values beyond which the device could be permanently damaged. absolute maximum ratings are stress ratings only and functional device operation is not implied. supply voltage (v cc ) ...................................... C0.3 to 7v gnd .................................................. C0.3 to v cc +0.3v logic inputs ......................................... C0.3 to v cc +0.3v input current per pin ............................................ 25ma storage temperature .................................. C65 to 150c package dissipation at t a = 25c ............................... 1w lead temperature (soldering 10 sec) ...................... 260c thermal resistance (q ja ) ...................................... 65c/w operating conditions supply voltage ................................................. 5v 10% temperature range ........................................ 0c to 70c
ML6420 4 electrical characteristics (continued) symbol parameter conditions min typ max units general (continued) output current r l = 0 (short circuit) 75 ma c l load capacitance 35 pf composite ML6420 (C1 to C4) f c = 5.5mhz 10 ns chroma/luma f c = 8.0mhz 8 ns delay at 3.58 ML6420 (C5 to C7) f c = 5.5mhz 15 ns & 4.43mhz f c = 9.3mhz 8 ns 3.0/3.3mhz filter C ML6420 bandwidth (monotonic passband) C3db (3.0mhz) 2.7 3.0 3.3 mhz C3db (3.3mhz) 3.0 3.3 3.6 mhz stopband attenuation f in = 9.82mhz (3.0mhz) 30 33 db f in = 9.82mhz (3.3mhz) 35 40 db f in = 60mhz 43 50 db output noise bw = 30mhz 490 v rms group delay 225 ns 5.50mhz filter C ML6420-1 bandwidth (monotonic passband) C3db 4.95 5.50 6.05 mhz stopband attenuation f in = 10mhz 16 18 db f in = 50mhz 40 45 db output noise bw = 30mhz 700 v rms group delay 145 ns 8.0mhz filter C ML6420 bandwidth (monotonic passband) C3db 7.2 8.0 8.8 mhz stopband attenuation f in = 17mhz 20 25 db f in = 85mhz 40 42 output noise bw = 30mhz 700 v rms group delay 120 ns
ML6420 5 electrical characteristics (continued) symbol parameter conditions min typ max units 5.50mhz filter C ML6420-5 bandwidth (monotonic passband) C3db (note 5) 4.95 5.50 6.05 mhz attenuation f in = 10mhz 20 25 db f in = 50mhz 45 55 db output noise bw = 30mhz 1 mv rms group delay 170 ns small signal gain v in = 100mv p-p at 100khz, 5.5 6 6.5 db filter a or c cv composite small signal gain v in a, c = 100mv p-p at 100khz 11 12 13 db 9.3mhz filter C ML6420-7 bandwidth (monotonic passband) C3db (note 5) 8.4 9.3 10.2 mhz attenuation f in = 17mhz 20 25 db f in = 85mhz 45 55 db output noise bw = 30mhz 1 mv rms group delay 100 ns digital and dc v il logic input low range 0.8 v v ih logic input high range v cc C 0.8 v i il logic input low v in = gnd C1 a i il logic input high v in = v cc 1a i cc supply current r l = 75w v in = 0.5v (note 4) 110 135 ma v in = 1.5v 150 175 ma note 1: limits are guaranteed by 100% testing, sampling, or correlation with worst case test conditions. note 2: maximum resistance on the outputs is 500 w in order to improve step response. note 3: connect all ground pins to the ground plane via the shortest path. note 4: power dissipation p d = (i cc v cc ) C [3 (v out 2 /r l )] note 5: the bandwidth is the C3db frequency of the unboosted filter. this represents the attenuation that results from boosting the gain from -3db point at the specified frequency.
ML6420 6 functional description the ML6420 single-chip dual/triple video filter ics are intended for low cost professional and consumer video applications. each channel incorporates an input buffer amplifier, a sixth order lowpass filter, a first order allpass equalizer, and an output 1x or 2x gain amplifier capable of driving 75 w to ground. when range is low the input and output signal range is 0.5v to 1.5v. when the input signal range is 0v to 1v, range should be tied high. in this case, an offset is added to the input so that the output swing is kept between 0.5v to 1.5v. the output amplifier is capable of driving up to 24ma of peak current; therefore the output voltage should not exceed 1.8v when driving 75 w to ground. the ML6420 can be driven by a dac with swing down to 0v. the summer output on the ml6422 is given by 2x(v ina + v inc ) C 2.5v when range = 0 and 2x(v ina + v inc ) C 0.5v when range is high. so, v ina and v inc should be such that this output does not go below 0.5v or above 2.5v for proper operation.
ML6420 7 application guidelines output considerations the triple filters have unity or 2x gain. the output circuit has unity or 2x gain (0db) when connected to a 150 w load, and a C6db gain when driving a 75 w load via a 75 w series output resistor. the output may be either ac or dc coupled. for ac coupling (figure 6), the C3db point should be 5hz or less. there must also be a dc path of 500 w to ground for biasing. the dual filters have 2x gain. the filter has 2x gain (6db) when connected to a 150 w load, and a 0db gain when driving a 75 w load via a 75 w series output resistor. the output may be either ac or dc coupled. for ac coupling, the C3db point should be 5hz or less. there must also be a dc path of 500 w to ground for output biasing. input considerations the input resistance is 4k w . the input may be either dc or ac coupled. (note that each input sources 80 to 125a of bias current). layout considerations in order to obtain full performance from these triple filters, layout is very important. good high frequency decoupling is required between each power supply and ground. otherwise, oscillations and/or excessive crosstalk may occur. a ground plane is recommended. each filter has its own supply and ground pins. in the test circuit, 0.1f capacitors are connected in parallel with 0.001f capacitors on pins v cc , v cc a, v cc b and v cc c for maximum noise rejection (figure 6a and figure 1g). further noise reduction is achieved by using series ferrite beads. in typical applications, this degree of bypassing may not be necessary. since there are three filters in one 16-pin soic package, space the signal leads away from each other as much as possible. power considerations the ML6420 power dissipation follows the formula: pi v v r dcccc out l = 16 C 2 3 this is a measure of the amount of current the part sinks (current in current out to the load). under worst case conditions: pmw d = = 0 175 5 5 15 75 3 872 5 2 .. C . . 05 power consumption can be reduced by not suppling v cc to unused filter sections. (v cc a, v cc b or v cc c) test circuits figures 6a shows the test circuitn used for measuring the frequency and group delay. it is expected that actual customer circuits will be much simpler, since board bypasses already exist and dc coupling or clamping will be utilized at the inputs. ML6420 video low pass filter filter selection: the ML6420 provides several choices in filter cut-off frequencies depending on the application.
ML6420 8 rgb: when the bandwidth of each signal is the same, then the 5.5mhz or 8.0mhz/9.3mhz are appropriate depending on the sampling rate. (13.5mhz vs 27mhz) yuv: when the luminance bandwidth is different from the color bandwidth, the ML6420-4 with the 8.0, 3.0 and 3.0mhz filters are more appropriate. s-video: for y/c (s-video) and y/c + cv (composite video) systems the ML6420 with 5.5mhz or 8.0mhz filters or ml6422 with 5.5mhz and 9.3mhz filters are appropriate. in ntsc the c signal occupies the bandwidth from about 2.6mhz to about 4.6mhz, while in pal the c signal occupies the bandwidth from about 3.4mhz to about 5.4mhz. in both cases, a 5.5mhz low pass filter provides adequate rejection for both sampling and reconstruction. in addition, using the same filter for both y/ c and cv maintains identical signal timing without adjustments. composite: when one or more composite signals need to be filtered, then the 5.50mhz, 8.0mhz, or 9.3mhz filters permit filtering of one, two or three composite signals. 4x over sampling: while the ML6420 filters can eliminate the need for over sampling combined with digital filtering, there are times when over sampling is needed. for these situations, 8.0mhz or 9.3mhz is used in place of 5.5mhz, and 3.0mhz is used in place of 1.8mhz. ntsc/pal: a 5.50mhz cut-off frequency provides good filtering for 4.2mhz, 5.0mhz. sinx/x: for digital video system with output d/a converters, there is a fall-off in response with frequency due to discrete sampling. the fall-off follows a sinx/x response. the ml6421 and ml6423 filters have a complementary boost to provide a flatter overall response. the boost is designed for 13.5mhz and 27mhz y/c and cv sampling and 6.75mhz or 13.5mhz u/v sampling. the ml6421 has the same pin-out as the ML6420. typical clamping schemes figures 8 and 9 show two typical applications of the ML6420 for anti-aliasing prior to a-to-d conversion. in figure 8, a single precision digital feedback clamp circuit includes both the adc and the ML6420. this establishes the proper dc operating point for the ML6420 (with range input = 0v, 0.5v v in 1.5v; with range input = 5v, 0.0 v in 1.0v.) and the adc. figure 8 is typically used with adcs that require external clamp circuitry. figure 9 shows ac coupled application for adcs with built-in clamps. in this case, the clamp is internal to the adc and the ML6420 uses a simple coarse clamp at its input to establish the proper operating point. using video filters the ML6420 are monolithic, triple/dual lowpass filters intended for input anti-aliasing prior to analog to digital conversion in video systems.
ML6420 9 aliasing: the problem aliasing is a signal distorting process that occurs when an analog signal is sampled. if the analog signal contains frequencies greater than half of the sampling rate, those frequencies will be altered and folded back in the frequency domain. these frequencies represent a distortion of the original signal as represented in the sampled domain, and cannot be corrected after sampling. the result of aliasing in a tv picture aliasing causes several disturbing distortions to a picture. since the folded spectrum adds to the original spectrum, it will sometimes be in phase, and sometimes out of phase causing ripples in response that depend on the position of the picture element relative to the clock. the net effect is that picture elements, edges, highlights, and details will wink in amplitude as they move across a picture if they have high frequency content above the nyquist frequency of the sampler. anti-aliasing anti-aliasing reduces the bandwidth of the signal to a value appropriate for the sample processing system. some detail information is lost, but only the information that cannot be unambiguously displayed is removed. assuming that the passband contains the real picture information, the only distortion that occurs is due to amplitude and phase variations of the anti-aliasing filter in the passband. the following section shows approaches using digital and analog filters in an oversampled system, and a monolithic analog filter as a lower cost alternative. oversampling aliasing cannot be removed once it occurs, it must be prevented at the signal sampler. many current systems are choosing to prevent aliasing by increasing the clock rate of the sampler. this is known as oversampling. doubling the clock rate greatly reduces the burden on the analog anti-alias filter, but the increased data rate greatly increases the size, complexity and cost of the digital signal processing (dsp) circuitry. since the higher clock rate generates more samples than are necessary to represent the desired passband content, a digital filter may be used to decimate the signal back to a lower sample rate, saving size, complexity and power in the downstream circuitry. since this digital filter itself is a complex digital block, this method cannot be considered the lowest cost approach to solving the anti-alias problem. nyquist sampling in traditional systems, before the advent of higher speed adcs, anti-aliasing filters were designed in the analog domain. the movement toward higher sampling rates was an attempt to circumvent the difficult challenge of designing a sharp roll-off, linear phase, non-distorting analog filter. the ML6420 series of filters solve this problem where it is best solved, in the analog domain. since they are monolithic, their application is simple. since they have flat amplitude and linear phase, they are low distortion. and since the aliasing is removed at the analog input to the adc, the clock rates are minimized, an expensive dsp half band filter is eliminated, and significant power is conserved. oversampling vs nyquist sampling clearly the purely analog monolithic solution versus the analog/digital solution using dsp filtering are different ways of solving the same problem. other than costs (purely analog is many times less expensive) there are no real differences in performance for applications that require flatness specs of 0.5db to 4.5mhz for consumer and pro-sumer video applications. the ML6420/ml6422 are also phase corrected for flat group delay, a feature not found in typical low cost analog filters, and a characteristic often associated with digital filters alone. the following section highlights the importance of linear phase response in video applications. time domain response: transients and ringing the phase response of filters is often ignored in applications where time domain waveforms are not relevant. but in video applications the time domain waveform is the signal that is finally presented on the screen to the viewer, and so time domain characteristics such as pulse response symmetry, pre-shoot, over-shoot and ringing are very important. video applications are very demanding in that they require both sharp cutoff characteristics and linear phase. the application of dsp to the problem is based on the linear phase characteristic of a particular class of digital filters known as symmetrical fir filters. use of these filters guarantees the best possible time domain characteristics for a given amplitude characteristic. in the analog domain phase linearity is not automatic (except for special phase linear filters such as bessel or thomson filters, both of which have inadequate amplitude characteristics for most video anti-alias applications) and it is often assumed that linear phase is unachievable. this is not true. similarly, in the digital domain it is often assumed that sharp cutoff amplitude characteristics can be achieved without overshoot and ringing. this is also not true. phase linear filters whether digital or analog have symmetrical response to symmetrical inputs. high roll-off rate uncompensated filters (whether analog or digital) have ringing and overshoot. in the example below, the traditional 2t test pulse is applied to a traditional, non-phase linear analog filter, the ML6420 pure analog anti-alias filter (5.5mhz) and the combined analog/digital filters (9.3mhz analog filter and half-band digital filter.) as seen in figure 19c, the ML6420 filters provide a time domain response that is comparable to more complex and expensive filters. typical passive filter
ML6420 10 typical analog filter figure 19a. ML6420 5.5mhz typ figure 19b. digital filter half-band figure 19c. the output waveform is not symmetric. all ringing occurs after the main pulse. result is visual smearing and fine ghosting to the right of every edge in the picture. see old figure 19a. phase corrected analog filter output waveform is substantially symmetric. ringing is greatly reduced. result is increase in apparent resolution. no smearing or ghosting. using video filters (continuied) analog filtering in the time domain output waveform is symmetric. ringing is about the same as ML6420 alone. difference between purely analog and analog/digital approach is subtle and will only have a material effect on multi-pass video processing.
ML6420 11 figure 1a. stop-band amplitude vs frequency (f c = 5.5mhz). ML6420 note: figure 1, 2 and 3 data was measured using the test circuit in figure 6. figure 3a. group delay vs frequency (f c = 5.5mhz). ML6420 figure 2a. pass-band amplitude vs frequency (f c = 5.5mhz). ML6420 10 0 C10 C20 C30 C30 C40 C50 C60 C70 C80 C90 relative amplitude (db) frequency (hz) 100k 1m 10m 100m +1 +0.25 C0.5 C1.25 C2.0 C2.75 C3.5 C4.25 C5.0 C5.75 C6.5 relative amplitude (db) frequency (hz) 100k 1m 10m 0 group delay (10ns/div) frequency (hz) ML6420-1 ML6420-5 2m 7m
ML6420 12 figure 2c. pass-band amplitude vs frequency (f c = 9.3mhz). ML6420 figure 2d. pass-band amplitude vs frequency (f c = 3mhz). ML6420 figure 1c. stop-band amplitude vs frequency (f c = 9.3mhz). ML6420 figure 1d. stop-band amplitude vs frequency (f c = 3mhz). ML6420 figure 3c. group delay vs frequency (f c = 9.3mhz). ML6420 figure 3d. group delay vs frequency (f c = 3mhz). ML6420 +5 0 C5 C10 C15 C20 C25 C30 C35 C40 C45 amplitude (db) frequency (hz) 100k 1m 10m +10 0 C10 C20 C30 C40 C50 C60 C70 C80 C90 amplitude (db) frequency (hz) 100k 1m 10m +3 +2 +1 0 C1 C2 C3 C4 C5 C6 C7 amplitude (db) frequency (hz) 100k 1m 10m +3 +2 +1 0 C1 C2 C3 C4 C5 C6 C7 amplitude (db) frequency (hz) 100k 1m 10m group delay (10ns/div) frequency (hz) ML6420-7 ML6420-3 1m 11m group delay (10ns/div) frequency (hz) 100k 5m
ML6420 13 figure 4. burst with 100ns pulse and fast transition at ML6420 output showing symetrical pulse response note: figure 4 and 5 data was measured using the test circuit in figure 7. figure 5. step with 2t and 12t response at ML6420 output showing accurate pulse response without overshoot or ringing figure 1h. cascading filters for sharper cutoff
ML6420 14 1 2 3 4 5 6 7 8 16 15 14 13 12 11 10 9 v in b v in a range gnda gnd v cc a v out a v out b gndb v in c gnd gndc v cc v cc c v out c v cc b 75 w 75 w outa outb 1 m f 0.1 m f 0.1 m f 100 m f 100 m f 3.1k w 47 w 1k w 85 w 47 w 85 w 3.1k w 1k w inb ina 0.1 m f 100 m f 1nf 1nf 1nf 1nf 0.1 m f 0.1 m f 0.1 m f 0.1 m f 0.1 m f 0.001 m f 1 m f 100 m f 75 w 85 w 47 w outc 3.1k w 1k w inc +5v fb2 fb1 dc bias input signal = 2v p-p input coupling supply noise clamping input termination 1 m f figure 6a. ML6420 ac coupled dc bias test circuit
ML6420 15 1k 100 w 100 w 150 w 2n3904 2n3904 + C 220 m f 0.1 m f 0.1 m f 0.1 m f + 2.5k 47k 1 m f 75 w 2.5k video input 1/3 ML6420 1/2 ml6422 input output 5v 131 w +5v +5v ad847(5v) a/d coarse clamp r g C5v optional 6db gain 2.5k gain = 1 + r g 1v p-p range figure 7. video clamp prior to a/d conversion
ML6420 16 analog video input digital video output ML6420/ml6422 anti-alias filter adc 8 digital clamp: ref level comparator 500 precision clamp circuitry (may be in adc module) analog video input digital video output ML6420/ml6422 anti-alias filter adc 8 digital clamp: ref level comparator 3 200 m f 500 coarse clamp circuitry v cc precision clamp circuitry (may be in adc) figure 8. dc coupled video digitizer for 2v pCp video signals figure 9. ac coupled video digitizer for 2v pCp video signals
ML6420 17 analog in adc signal processing analog out dac fs clock figure 10. simplified digital video processing system figure 11. aliasing in the frequency domain figure 12. aliasing in the time domain 0hz fs/2 fs 0 t desired passband signal content signal content at frequencies > fs/2 distortion from folded frequencies typical sampling clock high frequency elements that are on the clock will be sampled 100% elements that are off the clock will be missed
ML6420 18 analog in adc digital filter half-band analog out dac f 0 clock x2 figure 13. oversampled video processing system with analog lpf & half-band digital filter figure 14. digital filtering in the frequency domain figure 15. digital filtering in the time domain 0hz f 0 f 0 /2 2xf 0 0 t desired passband signal content analog/digital combo yields low aliasing errors analog filter reduces errors from f 0 to 2xf 0 at the input of the adc sampling clock at output high frequency elements that are reduced in amplitude and broadened to cover more than 1 pixel. ML6420 9.3mhz typ signal processing dsp filter reduces errors from f 0 /2 to f 0 at the output of the adc
ML6420 19 analog in adc analog out dac f 0 clock figure 16. video processing system with monolithic analog anti-alias filter figure 17. analog filtering in the frequency domain figure 18. analog filtering in the time domain 0hz f 0 /2 f 0 0 t desired passband signal content aliasing eliminated without increasing clock rates ML6420/ml6422 filter rolls-off all errors above f 0 /2 sampling clock at output ML6420/ml6422 achieves virtually same results as dsp filters. ML6420 5.5mhz typ signal processing
ML6420 20 ds6420-01 physical dimensions inches (millimeters) 2092 concourse drive san jose, ca 95131 tel: (408) 433-5200 fax: (408) 432-0295 www.microlinear.com seating plane 0.291 - 0.301 (7.39 - 7.65) pin 1 id 0.398 - 0.412 (10.11 - 10.47) 0.400 - 0.414 (10.16 - 10.52) 0.012 - 0.020 (0.30 - 0.51) 0.050 bsc (1.27 bsc) 0.022 - 0.042 (0.56 - 1.07) 0.095 - 0.107 (2.41 - 2.72) 0.005 - 0.013 (0.13 - 0.33) 0.090 - 0.094 (2.28 - 2.39) 16 0.009 - 0.013 (0.22 - 0.33) 0o - 8o 1 0.024 - 0.034 (0.61 - 0.86) (4 places) package: s16w 16-pin wide soic part number bw (mhz) gain temperature range package ML6420cs-1 (eol) 5.5/5.5/5.5 1x 0c to 70c 16-pin soic (s16w) ML6420cs-3 8.0/8.0/8.0 1x 0c to 70c 16-pin soic (s16w) ML6420cs-4 (eol) 8.0/3.0/3.0 1x 0c to 70c 16-pin soic (s16w) ML6420cs-5 (eol) 5.0/5.0/5.0 2x 0c to 70c 16-pin soic (s16w) ML6420cs-7 (eol) 9.3/9.3/9.3 2x 0c to 70c 16-pin soic (s16w) ordering information ? micro linear 2000. is a registered trademark of micro linear corporation. all other trademarks are the property of their respective owners. products described herein may be covered by one or more of the following u.s. patents: 4,897,611; 4,964,026; 5,027,116; 5,281,8 62; 5,283,483; 5,418,502; 5,508,570; 5,510,727; 5,523,940; 5,546,017; 5,559,470; 5,565,761; 5,592,128; 5,594,376; 5,652,479; 5,661,427; 5,663,874; 5,672,959; 5,689,167; 5,714,897; 5,717,798; 5,742,151; 5,747,977; 5,754,012; 5,757,174; 5,767,653; 5,777,514; 5,793,168; 5,798,635; 5,804,950; 5,808,455; 5,811,999; 5,818,207; 5,818,669; 5,825,165; 5,825,223; 5,838,723; 5.844,378; 5,844,941. japan: 2,598,946; 2,619,299; 2,704,176; 2,821,714. other patents are pending. micro linear makes no representations or warranties with respect to the accuracy, utility, or completeness of the contents of t his publication and reserves the right to make changes to specifications and product descriptions at any time without notice. no license, expr ess or implied, by estoppel or otherwise, to any patents or other intellectual property rights is granted by this document. the circu its contained in this document are offered as possible applications only. particular uses or applications may invalidate some of the specifi cations and/ or product descriptions contained herein. the customer is urged to perform its own engineering review before deciding on a par ticular application. micro linear assumes no liability whatsoever, and disclaims any express or implied warranty, relating to sale and /or use of micro linear products including liability or warranties relating to merchantability, fitness for a particular purpose, or infri ngement of any intellectual property right. micro linear products are not designed for use in medical, life saving, or life sustaining applic ations.

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